Method and apparatus for a high voltage power supply circuit

ABSTRACT

A power converter is disclosed. An example power converter includes an energy transfer element coupled between a power converter input and a power converter output. A power switch is coupled to the energy transfer element. A control circuit is coupled to receive a feedback signal representative of the power converter output during a feedback portion of an off time of the power switch. The control circuit is coupled to generate an output signal in response to the feedback signal. The output signal is coupled to be received by the power switch to control switching of the power switch to control a fraction of the feedback portion of the off time of the power switch that the feedback signal is above a threshold and another fraction of the feedback portion of the off time of the power switch that the feedback signal is below the threshold.

REFERENCE TO PRIOR APPLICATION(S)

This application is a continuation of U.S. application Ser. No.12/047,129, filed Mar. 12, 2008, now U.S. Pat. No.7,936,159, whichclaims the benefit of U.S. Provisional Application No. 60/919,842, filedMar. 23, 2007, entitled “METHOD AND APPARATUS FOR A HIGH VOLTAGE POWERSUPPLY CIRCUIT.” U.S. application Ser. No. 12/047,129 and U.S.Provisional Application No. 60/919,842 are hereby incorporated byreference.

BACKGROUND INFORMATION

1. Field of the Disclosure

The present invention relates generally to control circuits and, morespecifically, the present invention relates to control circuits used ina power converter that regulate the power converter output.

2. Background

Power converter control circuits may be used for a multitude of purposesand applications. Due to requirements to reduce power converter cost,there is a demand for control circuit functionality to reduce externalcomponent count for components external to the integrated controlcircuit. This reduction in external component count enablesminiaturization of the power converter to improve portability, reducesthe number of design cycles required to finalize a power converterdesign and also improves reliability of the end product. Furthermore,reduced component count can offer energy efficiency improvements in theoperation of the power converter and can reduce the power convertercost. One aspect of the power converter offering the potential forcomponent count reduction is in simplifying or removing the externalcircuitry previously required to achieve output voltage regulation in apower converter.

In isolated flyback converters used for AC/DC power conversion, theoutput voltage is typically measured across the isolated power supplyoutput terminals to generate a continuous feedback signal that iscoupled to a control circuit on the primary, also referred to as theinput, of the power supply, typically employing an opto-coupler toprovide isolation between power supply input and output circuitry. Thecontrol circuit is responsive to the feedback signal to controlswitching of a power switch coupled to a winding of an energy transferelement to regulate power delivered from the input to the output of thepower converter.

In other flyback converters, a feedback signal is generated using anauxiliary winding forming part of the power converter transformer orenergy transfer element. The flyback voltage across the auxiliarywinding is rectified and smoothed to generate a feedback signal that iscoupled to a control circuit on the primary side of the converter.

In buck converters a feedback signal representative of the powerconverter output voltage is typically generated by rectifying andsmoothing the voltage across the main inductor or energy transferelement winding during the off time of a power switch.

In both flyback and buck converter configurations, the power switch iscoupled to a power supply input and to the energy transfer element suchthat a current flows from the power supply input through the powerswitch and the energy transfer element when the power switch is in an ONstate.

BRIEF DESCRIPTION OF THE DRAWINGS

Non-limiting and non-exhaustive embodiment and examples of the presentinvention are described with reference to the following figures, whereinlike reference numerals refer to like parts throughout the various viewsunless otherwise specified.

FIG. 1 is a schematic illustrating generally an example flyback powersupply employing a control circuit responsive to a feedback signal thatmay regulate an output of the power supply in accordance with theteachings of the present invention.

FIG. 2 shows generally waveforms for a power supply employing an examplecontrol circuit responsive to a feedback signal to regulate an outputvoltage of a power supply in accordance with the teachings of thepresent invention.

FIG. 3 shows generally waveforms for a power supply employing an examplecontrol circuit responsive to a feedback signal to regulate an outputvoltage of a power supply in accordance with the teachings of thepresent invention.

FIG. 4 is a more detailed schematic illustrating a portion of an examplecontrol circuit in accordance with the teachings of the presentinvention.

FIG. 5 is a schematic illustrating generally an example non-isolatedpower supply employing a control circuit responsive to a feedback signalthat may regulate an output voltage of the power supply in accordancewith the teachings of the present invention.

FIG. 6 is a more detailed schematic illustrating a portion of anotherexample control circuit in accordance with the teachings of the presentinvention.

FIG. 7 is a flowchart illustrating an example method for regulating anoutput voltage of a power supply in accordance with the teachings of thepresent invention.

FIG. 8 shows a more detailed schematic of a portion of the internalcircuitry of yet another example of a control circuit in accordance withthe teachings of the present invention.

DETAILED DESCRIPTION

Methods and apparatuses for implementing a control circuit forregulating a power converter output are disclosed. In the followingdescription, numerous specific details are set forth in order to providea thorough understanding of the present invention. It will be apparent,however, to one having ordinary skill in the art that the specificdetail need not be employed to practice the present invention. In otherinstances, well-known materials or methods have not been described indetail in order to avoid obscuring the present invention.

Reference throughout this specification to “one embodiment”, “anembodiment”, “one example” or “an example” means that a particularfeature, structure or characteristic described in connection with theembodiment or example is included in at least one embodiment of thepresent invention. Thus, appearances of the phrases “in one embodiment”,“in an embodiment”, “one example” or “an example” in various placesthroughout this specification are not necessarily all referring to thesame embodiment or example. Furthermore, the particular features,structures or characteristics may be combined in any suitablecombinations and/or subcombinations in one or more embodiments orexamples. In addition, it is appreciated that the figures providedherewith are for explanation purposes to persons ordinarily skilled inthe art and that the drawings are not necessarily drawn to scale.

A control circuit for regulating a power converter output in accordancewith the teachings of the present invention will now be described.Examples of the present invention involve methods and apparatuses toregulate a power converter output.

FIG. 1 shows generally a schematic of a power converter 100, alsoreferred to herein as a power supply, employing a control circuit thatregulates an output voltage of the power converter in accordance withthe teachings of the present invention. In one example, power converter100 is an isolated flyback converter where primary ground 107 andsecondary return 126 are isolated from one another. It is noted that inother examples, power converter 100 could also be a non-isolated flybackconverter in accordance with the teachings of the present invention. Itis noted that in other examples power converter 100 could have more thanone output in accordance with the teachings of the present invention.

As shown, a control circuit 115 is coupled to a power switch 105, whichin one example is a metal oxide semiconductor field effect transistor(MOSFET) semiconductor switch, a bipolar transistor or the like. Powerswitch 105 is coupled to an input winding 103 of energy transfer element109, which is coupled to a DC input voltage 101 and an output powerdiode 117. In one example, DC input voltage 101 is the output of arectifier circuit coupled to a source of AC voltage not shown. Capacitor106 is coupled to power converter input terminals 190 and 191 to providea low impedance source for switching currents flowing through first andsecond input terminals 190 and 191, energy transfer element 109 winding103 and power switch 105 when the power switch 105 is in an ON state. Inone example, control circuit 115 and switch 105 could form part of anintegrated circuit that could be manufactured as a hybrid or monolithicintegrated circuit. Control circuit 115 is coupled to receive a feedbacksignal 114, which in one example is a voltage signal, but in anotherexample could be a current signal or other signal indicative of thepower supply output while still benefiting from the teachings of thepresent invention.

In the example, control circuit 115 is coupled to regulate energydelivered from the first and second input terminals 190 and 191 of powerconverter 100 to the power converter output terminals 192 and 193coupled to load 121. In one example, the specific output parameter beingregulated is the DC output voltage 119. Energy transfer element 109comprises input winding 103 and output winding 110 and an auxiliarywinding 108. The feedback signal 114 is coupled to control circuit 115from auxiliary winding 108 through the resistor divider formed byresistors 111 and 112.

In operation, control circuit 115 regulates the output of power supply100 by switching power switch 105 in response to the feedback signal114. When switch 105 is on, energy from the capacitor 106 is transferredinto the input winding 103 of the energy transfer element 109. When theswitch is off, the energy stored in the input winding 103 is transferredto the output winding 110. The energy from output winding 110 istransferred to the output of the power supply 100 with a current thatflows through a forward biased output power diode 117 to outputcapacitor 118 and the load 121 coupled to the output terminals 192 and193. While current flows through the output power diode 117 during theoff period of switch 105, the output voltage V_(O) 119 across load 121plus the forward voltage drop across output power diode 117 issubstantially equal to the voltage across the output winding 110.

As will be discussed, this portion of the off time of the power switchwhen the voltage across the output winding 110 is representative of theoutput voltage V_(O) 119 while current flows through the output diodewill be referred to as a feedback portion T_(FB) of the off time of thepower switch 105. In some cases, the current may substantially stopflowing from output winding 110 through the output power diode 117during the off period of power switch 105. In this case, the outputpower diode 117 becomes reversed biased and the voltage drop acrossoutput winding 110 is no longer representative of the output voltageV_(O) 119. This portion of the off time of the power switch 105 whensubstantially no current flows through output power diode 117 may bereferred to as the no feedback portion of the off time of the powerswitch 105.

The voltage across the output winding 110 is reflected to an auxiliarywinding 108 of the energy transfer element based on the turns ratio. Thevoltage across the auxiliary winding 108 may therefore be employedduring the feedback portion T_(FB) of the off time of the power switch105 to obtain a feedback signal 114 regarding the output of power supply100, which is coupled to be received by the control circuit 115 tocontrol switching of the power switch 105 to regulate the output ofpower supply 100.

In one example, a circuit block 194 coupled to the auxiliary winding 108includes a diode 113 as shown in FIG. 1. During the on time of powerswitch 105, auxiliary winding diode 113 is reverse biased and thereforeprevents current flow in resistors 111 and 112. In another example,circuit block 194 includes a substantially short circuit connection 195as shown while still benefiting from the teachings of the presentinvention.

In the example where circuit block 194 includes the substantially shortcircuit connection 195, a signal is applied to terminal 123 of controlcircuit 115 during the on time of the power switch 105. However, thissignal is a feedforward signal that is not representative of the outputvoltage of the power converter. Thus, in the example where circuit block194 includes the substantially short circuit connection 195, signal 114is still therefore only a feedback signal representative of the outputvoltage 119 of power converter 100 during the off time of power switch105. In one example, signal 114 is a feedback signal representative ofthe output voltage 119 of power converter 100 during only a portion ofthe off time of power switch 105, as will now be described withreference to the example illustrated in FIG. 2.

FIG. 2 shows example waveforms that help illustrate the operation of theexample circuit of FIG. 1. For instance, waveform 200 is a voltagewaveform of V_(FB) 116 in FIG. 1. As will be discussed, waveform 200 maybe used in one example to provide feedback to the control circuit 115regarding the output voltage V_(O) 119 during a feedback portion T_(FB)205 of the off period Toff 206 of waveform 200. In the illustratedexample, no feedback information is provided during the no feedbackportion T_(NFB) 216 of waveform 200. Waveform 214 is a current waveformof the Drain current 104 flowing in power switch 105 in FIG. 1. In theillustrated example, the waveform 214 is shown as a discontinuouscurrent waveform since the Drain current waveform 209 starts fromsubstantially zero current 215 each time the power switch 105 turns on.

In each switching cycle, the power switch is on for an on time periodTon 204 and is off for an off time period Toff 206. During the feedbackportion T_(FB) 205 of off time Toff 206, output power diode 117 isforward biased such that current is flowing in the output power diode117 of power converter 100. The voltage appearing across output winding110 at this time during T_(FB) 205 is therefore substantially equal tooutput voltage 119 plus the forward bias voltage drop of power diode117. It is noted that during the no feedback portion T_(NFB) 216 of theoff time Toff 206 shown in the example of FIG. 2, output diode 117 is nolonger forward biased and no substantial current flows through theoutput power diode 117. At this time during T_(NFB) 216, the voltageappearing across output winding 110 does not provide feedbackinformation regarding output voltage 119.

When output power diode 117 is forward biased, the amount of currentthat flows in output power diode 117 is substantially equal to a sum ofa current flowing in the output capacitor 118 and output current 120flowing in the load 121. Since the forward voltage of diode 117 whilecurrent is flowing through diode 117 is substantially known throughmanufacturers data, the voltage appearing across winding 110 istherefore representative of the output voltage 119. Furthermore, thevoltage appearing across winding 108 is related to the voltage acrosswinding 110 through the turns ratio of windings 110 and 108. In otherwords, the voltage across winding 110 is reflected onto the voltageacross winding 108 depending on the respective turns ratio. For example,if windings 110 and 108 have the same number of turns, the voltageappearing across winding 110 and winding 108 during the feedback portionT_(FB) 205 of the off time Toff 206 will, to a first order, besubstantially equal. Second order influences such as leakage inductanceand interwinding capacitance are not detailed here so as not to obscurethe teachings of the present invention. During the feedback portionT_(FB) 205 of the off time Toff 206, the voltage appearing acrosswinding 108 is therefore also representative of output voltage 119.

Since feedback signal 114, which in this example is V_(FB) 116, isrelated to the voltage appearing across winding 108 through the knowncircuit block 194 and resistor divider formed by resistors 111 and 112,the feedback signal 114 is representative of an output voltage of thepower supply during the feedback portion T_(FB) 205 of the off time Toff206 of the switch. It will be noted that there is a slope, exaggeratedin FIG. 2 for the purposes of explanation, on feedback voltage waveform208 during the feedback portion T_(FB) 205 of the off time Toff 206primarily due to impedances in the output circuit of the power supply.Such impedances include the forward impedance of diode 117, whichincludes a resistive element and a series impedance of output capacitor118, which includes a resistive element.

It is noted that during the power switch 105 on time period Ton 204, thevoltage appearing at feedback terminal 123 in FIG. 1 is substantiallyzero volts relative to ground terminal 124 if circuit block 194comprises a diode 113 or if there is an internal clamp (not shown)coupled to terminal 123. This case is shown by voltage level 213 in FIG.2 which is substantially equal to the ground voltage 202.

In an example circuit configuration where the control circuit 115 inFIG. 1 does not have an internal clamp coupled to terminal 123 and whenthe circuit block 194 comprises the substantially short circuitconnection 195, the voltage appearing at feedback terminal 123 willfollow a characteristic of the type shown by dotted line 203 in FIG. 2.In either case, the feedback signal 208 in the illustrated example isonly representative of an output voltage 119 of the power converter 100during the feedback portion 205 of the off time Toff 206.

FIG. 3 shows example waveforms that further help illustrate theoperation of the circuit of FIG. 1. Waveform 300 is a voltage waveformof V_(FB) 116 in FIG. 1. Waveform 314 is a current waveform of the Draincurrent 104 flowing in power switch 105 in FIG. 1. The example waveform314 shown in FIG. 3 is a continuous current waveform since the Draincurrent waveform 309 starts rising from a non-zero current level 315after each time the power switch 105 turns on. In each switching cycle,the power switch is on for an on time period Ton 304 and is off for anoff time period Toff 306.

In the example waveforms illustrated in FIG. 3, it is noted that thefeedback portion T_(FB) 305 of off time Toff 306 is substantially equalto the entire off time Toff 306. This indicates that the power outputpower diode 117 is forward biased and that current is therefore flowingin the power output power diode 117 for substantially all of the offtime period of the power switch 105. The voltage appearing across outputwinding 110 is therefore substantially equal to output voltage 119 plusthe forward voltage drop of diode 117 during the entire off time periodToff 306. By the same explanation applied to the waveforms of FIG. 2above therefore, feedback signal 114 or V_(FB) 116 is representative ofthe output voltage of the power converter during T_(FB) 305, which inthe case of FIG. 3 is substantially the entire off time period Toff 306of the power switch 105.

FIG. 4 shows generally a schematic of a circuit 400, which may be a moredetailed example schematic of a portion of control circuit 115 in FIG. 1in accordance with the teachings of the present invention. The circuitryof FIG. 4 is one example of a circuit that, when coupled to receive afeedback signal representative of an output voltage of a power converterduring the feedback portion 205 or 305 of the off time of the switch,could regulate power delivery from an input of a power converter to anoutput of the power converter in accordance with the teachings of thepresent invention.

As shown in the depicted example, control circuit 415 is coupled toreceive a feedback signal V_(FB) 416 at feedback terminal 423 relativeto ground terminal 424. In one example, control circuit 415 includesfeedback circuitry, which includes comparator 453, switches 456, 457,459, feedback capacitor 460 and current sources 455 and 458. Feedbackvoltage V_(FB) 416 is coupled to non-inverting input 450 of comparator453. A reference voltage V_(REF) 452 is applied to inverting input 451of comparator 453. In one example, reference voltage V_(REF) 452 isequivalent to voltage threshold value 201 in FIG. 2 and voltagethreshold value 301 in FIG. 3. The output of comparator 453 is coupledto drive transistor switches 456 and 457 such that, when V_(FB) 416 is>V_(REF) 452, switch 457 is turned on and when V_(FB) 416 is <V_(REF)452 switch 456 is turned on.

As shown in the illustrated example, circuit block 461 is coupled todrive switch 459 such that switch 459 is in an on state only during thefeedback portion T_(FB) 205 of the off period Toff 206 in the example ofFIG. 2, or T_(FB) 305 in the example of FIG. 3. Current can thereforeonly flow into or out of feedback capacitor 460 during T_(FB) 205 or305. In one example, circuit block 461 is coupled to determine thefeedback portion T_(FB) 205 of the off period 206 by comparing feedbacksignal 416 with a threshold voltage level to drive switch 459 with alogic high input signal when feedback signal 416 is greater than thethreshold voltage level to determine whether the output power diode 117is conducting current. The duration for which switch 459 is driven bycircuit block 461 with the logic high input signal is substantiallyequal to the period T_(FB) 205 when current flows through power outputdiode 117 in FIG. 1. The voltage V_(PWM) 464 appearing across feedbackcapacitor 460 is coupled to pulse width modulator (PWM) comparator 463and compared to a PWM waveform 462 to generate a variable duty cycleoutput 422 at output terminal 425 in response to the magnitude of thevoltage V_(PWM) 464. In one example, PWM waveform 462 is a ramp signalor a triangular waveform or the like.

In one example, PWM comparator 463 is part of a signal generator ofcircuit 400 to generate signal 422, which could be equivalent to signal122 in FIG. 1. In one example, the signal generator could include anoscillator providing a signal to initiate the on time of the powerswitch cycle. The oscillator signal could be substantially fixed infrequency, or its frequency can be modulated to reduce EMI in thesystem, or be varied under certain conditions to reduce powerconsumption or increase efficiency without departing from the teachingsof the invention. In another example, the signal generator could alsoinclude circuitry to logically combine other signals with signal 422 togenerate signal 122 such as protective current limit and thermalshutdown signals and the like in accordance with the teachings of thepresent invention. It is noted that in another example, the voltageV_(PWM) 464 could also be filtered with a low pass filter coupledbetween feedback capacitor 460 and the non-inverting input of PWMcomparator 463 in accordance with the teachings of the presentinvention.

In the illustrated example, since current can only flow in transistorswitch 459 when it is in an on state, the voltage V_(PWM) 464 is onlyresponsive to the output of comparator 453 and therefore the feedbacksignal 416, during the feedback portion T_(FB) 205 in FIG. 2 or 305 inFIG. 3 of the off time Toff 206 or 306. Continuing with the exampledescribed above, feedback capacitor 460 is discharged with a current I2458 through transistor switch 459 during a portion of the feedbackportion T_(FB) 205 or 305 while the feedback signal voltage 416 isgreater than the reference voltage V_(REF) 452. Referring back to theexamples shown in FIG. 2 and FIG. 3, this corresponds to the portions ofT_(FB) 205 or T_(FB) 305 that are labeled as time periods K×T_(FB) 207in FIG. 2 or K×T_(FB) 307 in FIG. 3, respectively, where K is a variablehaving a value less than 1. Remaining portions of T_(FB) 205 or T_(FB)305 are labeled as time periods (1−K)×T_(FB) 210 in FIG. 2 or(1−K)×T_(FB) 310 in FIG. 3, respectively. In the (1−K)×T_(FB) portions,the feedback capacitor 460 is charged with a current I1 455 throughtransistor switch 459 while the feedback signal voltage 416 is less thanthe reference voltage V_(REF) 452.

In an example where current I1 455 and current I2 458 are substantiallyequal, the average of voltage V_(PWM) 464 will remain constant ifvariable K has a value substantially equal to 0.5. During the operationof power converter 100, if output current 120 suddenly increases, theoutput capacitor 118 starts to discharge and output voltage 119 isreduced. As a consequence, the feedback voltage V_(FB) 416 during thefeedback portion T_(FB) 205 of the off time Toff 206 of power switch 105is also reduced. This example is illustrated in FIG. 2 where thefeedback signal voltage 222 during feedback portion T_(FB) 205 isreduced compared to the feedback signal voltage 208, which representsthe feedback signal level when the load current 120 in FIG. 1 is stable.Under this transient load condition, the feedback signal voltage duringfeedback portion T_(FB) 205 is greater than the reference voltagethreshold value 201 for a time Tx 221, which is less than the timeperiod 207 under stable load conditions.

Referring back to FIG. 4, therefore, since the feedback signal voltage416 during time period 205 is greater than the reference voltagethreshold value 452 for a shorter time, feedback capacitor 460 isdischarged for a shorter time resulting in the voltage V_(PWM) 464across feedback capacitor 460 increasing. This in turn increases theduty cycle of the output signal 422, which in one example results in anincrease in the on time percentage or duty cycle of the power switch 105in FIG. 1. The power delivered to the power supply output thereforeincreases tending to bring the feedback voltage in FIG. 2 back to steadystate level 208. This restores the condition of equal charge anddischarge of feedback capacitor 460 in FIG. 4 such that the averagevoltage of V_(PWM) 464 becomes substantially constant.

It will be noted that a similar explanation could be applied to thewaveforms of FIG. 3. It will also be noted that the opposite effecthappens when a transient reduction in power converter load occurs andthe duty cycle of output signal 422 is reduced until a new stable dutycycle is reached. It is noted that under certain transient loadconditions, the feedback signal level may transiently be greater than orless than voltage threshold values 201 and 301 for the entire periodT_(FB) 205 and 305. Under these conditions feedback capacitor 460 inFIG. 4 is either charged or discharged for the entire period T_(FB) 205and 305 for as long as this condition exists. The effect on the dutycycle of signal 422 is to return the feedback signal to a level wherethe feedback signal value is greater than threshold values 201 an 301for a portion of period T_(FB) 205 and 305 and less than thresholdvalues 201 and 301 for the remainder of time period T_(FB) 205 and 305.

It is noted that although the circuit of FIG. 4 varies duty cycle ofoutput signal 422 by comparing voltage V_(PWM) 464 with reference PWMramp signal 462, in a manner sometimes referred to as voltage modecontrol, there are many ways that this duty cycle control could beaccomplished. For instance, in one example, a threshold to be comparedto the current flowing in the power switch 105 could be madeproportional to the V_(PWM) 464 voltage, which would also result inincreased power switch duty cycle with increasing V_(PWM) 464 voltage ina manner sometimes referred to as current mode control. In anotherexample, the switching period T 212 in FIGS. 2 and 312 in FIG. 3 couldbe made inversely proportional to the V_(PWM) 464 voltage while holdingthe power switch on time period 204 or 304 in FIGS. 2 and 3respectively, substantially constant, which again would also result inincreased power switch duty cycle with increasing V_(PWM) 464 voltage ina manner sometimes referred to as variable frequency control. In anotherexample, any combination of these control techniques could be used toregulate power delivery from the input to the output of the powerconverter to regulate an output voltage of the power converter inaccordance with the teachings of the present invention.

In accordance with the above description therefore, and with referenceto FIGS. 1, 2, 3 and 4, in one example, control circuits 115 and 415control switching of a power switch to regulate the time periods 207 and210 of the feedback portion T_(FB) 205, or the time periods 307 and 310of the feedback portion T_(FB) 305 that the respective feedback signal114, 208, 308 or 416 are above a threshold value. The respectivefeedback signal 114, 208, 308 or 416, representative of a powerconverter output voltage is received only during the feedback portionT_(FB) 205 or T_(FB) 305 of an off time 206 or 306 of the power switch105. In this way, the control circuit 115 in power converter 100regulates power delivery from the input to the output of the powerconverter to regulate an output voltage of the power converter.

It is noted that by designing current sources I1 455 and I2 458 to beunequal, the value of variable K in FIGS. 3 and 4 can be any fraction.In one example, if the value of I2 458 is made less than the value of I1455, the steady state condition for the voltage across feedbackcapacitor 460 is when the value of K is >0.5. The (K×T_(FB)) product 207or 307 will then be greater than 50% of T_(FB) 205 and 305 and the((1−K)×T_(FB)) product 210 or 310 will then be less than 50% of T_(FB)205 and 305 in this example. In some examples there may be an advantageto selecting a value of K>0.5. For instance, one reason could be due tothe inherent resistive voltage drop across diode 117 in FIG. 1. Inparticular, the resistive voltage drop across one example of diode 117is lower toward the end of the feedback portion T_(FB) 205 or 305 sincethe current flowing in the diode 117 is lower in this region. Theresistive voltage drop is therefore lower so the feedback signal is morerepresentative of the power converter output voltage 119 in thisexample.

In one example, the variable K is varied or modified according to theoperating conditions of the power converter. For example, with referenceto FIG. 1, in an application where the impedance of output connection199 is relatively large, there can be an appreciable voltage drop acrossthis connection often referred to as an output cable. In order to helpmaintain a stable supply voltage across the load 121 in such an example,output voltage 119 is increased as a function of increasing outputcurrent 120. In other examples the voltage dropped across output powerdiode 117 can vary as a function of the output current 120, when forexample the peak primary current 104 flowing in power switch 105 iscontrolled as a way of regulating power delivery from an input of thepower converter 100 to an output of the power converter in accordancewith the teachings of the present invention. The circuit of FIG. 4 showsoptional circuitry including a circuit block 471 and variable currentsource 470 that can be implemented to compensate for diode voltage dropor cable drop variations. The function of circuit block 471 is to outputa signal 472 to control current source 470 such that the current I3 ofcurrent source 470 is increased as the T_(FB)/T ratio of circuit block471 increases.

In operation, the ratio of the output power diode 117 conduction timeT_(FB) 205 and 305 with the overall switching period T 212 and 312 isone indication of the magnitude of the power converter output current.If current source 470 current I3 is increased as the ratio T_(FB)/Tincreases, then the value of variable K in FIGS. 2 and 3 is thereforealso increased since transistor switch 456 needs to be on for less timeto maintain the voltage on feedback capacitor 460. With reference forFIGS. 2 and 3 therefore, time periods 207 and 307 will increase as thecurrent source 470 current I3 in FIG. 4 is increased in accordance withthe teachings of the present invention. The effect is to effectivelyraise the average value of the feedback signal 208 and 308, which inturn raises the value of power converter output voltage 119. In anexample application with this functionality, additional current I3 wouldrepresent approximately 0-5% of the main I1 455 current value, dependingon the load conditions. The effect of the operation described above isthat the time that the feedback signal 208 and 308 is above thethreshold value 201 and 301 is varied according to a magnitude of thecurrent Io 120 flowing in the power supply output terminals inaccordance with the teachings of the present invention.

In other examples, the variable K could be changed based on otherfactors such as the temperature of one or more components includedwithin the power converter or for example the ambient temperature inwhich the power converter is operating.

It is noted that in the above description, the specific way that thepower converter 100 is regulated could alternatively be described interms of the control circuit 115 and 415 controlling switching of thepower switch 105 to regulate either one or both of the time periods 207or 210 and/or time periods 307 or 310 of T_(FB) 205 or T_(FB) 305,respectively, in accordance with the present invention. Indeed, it isappreciated that by regulating the time period 207 of T_(FB) 205, whichis equal to K×T_(FB), the time period 210 of T_(FB) 205 is alsoregulated, which is equal to (1−K)×T_(FB). Similarly, by regulating thetime period 210 of T_(FB) 205, the time period 207 of T_(FB) 205 is alsoregulated.

FIG. 5 shows a schematic 500 of an example non-isolated power converterin accordance with the teachings of the present invention. In theillustrated example, the non-isolated power converter shown is a buckconverter. It is appreciated that other types of non-isolated powersupplies may also benefit from the teachings of the present invention,including for example but not limited to boost converters, buck-boostconverters, SEPIC converters, Ćuk converters or the like. In theillustrated example, control circuit 515 shares many aspects of itsoperation with the control circuits 115 and 415 described above. In oneexample, there is no requirement for an auxiliary winding on the energytransfer element and instead, a feedback signal 514 having a voltagevalue V_(FB) 516 is coupled to the control circuit 515 from the mainenergy transfer element 509 winding 594.

In operation, when power switch 505 is on, current 504 flows betweenfirst 591 and second 592 input terminals of the power supply 500 throughthe energy transfer element 509 and the power switch 505. In one examplepower switch 505 is a MOSFET semiconductor switch, a bipolar transistoror the like. When power switch 505 is off, the voltage at node 593 dropsto a value substantially equal to the ground voltage 507 minus theforward voltage drop across output power diode 530, which is coupled toenergy transfer element 509, to sustain current flow in energy transferelement 509 during a feedback portion T_(FB) of the power switch 505 offtime. During this feedback portion T_(FB) of the power switch 505 offtime, which is when output power diode 530 is conducting current, thevoltage across energy transfer element 509 is therefore equal to outputvoltage 519 plus a forward diode voltage drop across output power diode530 and is therefore representative of the output voltage 519 during thefeedback portion T_(FB) of the power switch 505 off time. The currentthat flows in output power diode 530, is substantially equal to a sum ofa current flowing in the output capacitor 518 and output current 520flowing in the load 521. As shown in the example, the voltage acrossenergy transfer element winding 594 is coupled through circuit block 513and resistor divider formed by resistors 511 and 512 to feedbackterminal 523 of control circuit 515 as a feedback signal 514.

In the illustrated example, the feedback signal 514 is coupled tocontrol circuit 515 from energy transfer element 509 winding 594 onlyduring the off time of power switch 505. In one example, circuit block513 includes a diode 595 coupled to the main energy transfer elementwinding 594. During the on time of power switch 505, diode 595 isreverse biased and therefore prevents current flow in resistors 511 and512.

In another example, circuit block 595 includes a substantially shortcircuit connection 596 as shown while still benefiting from theteachings of the present invention. In this example where circuit block595 includes the substantially short circuit connection 596, a signal isapplied to terminal 523 of control circuit 515 during the on time of thepower switch 505. However this signal during the on time of the powerswitch 505 is not representative of the output voltage of the powerconverter. In an example where circuit block 513 comprises thesubstantially short circuit connection 596, the feedback signal 514 isstill therefore only a feedback signal representative of the outputvoltage 519 of power converter 500 during the feedback portion T_(FB) ofthe power switch 505 off time, which is while there is current flowingin output power diode 530. In one example of the buck converter circuitof FIG. 5, circuit block 513 includes a diode 595 to help ensure thatthe feedback signal 514 having the voltage value V_(FB) 516 is a moreaccurate representation of output voltage 519, since the forward voltagedrop across diode 595 tends to cancel the forward voltage drop acrossoutput power diode 530.

Thus, in one example, the principle of operation of control circuit 515is similar to that of control circuits 115 and 415 above. The feedbackportion T_(FB) of power switch 505 off time ends when the currentflowing in output power diode 530 falls to substantially zero valuesince the voltage across energy transfer element 509 is onlyrepresentative of output voltage 519 while the current flowing in outputpower diode 530 is non-zero. The control circuit 515 is coupled toregulate the portions of the feedback portion T_(FB) of power switch 505off time that feedback voltage V_(FB) 516 is above and below a thresholdvalue that is generated within the control circuit 515. In one examplethe circuitry discussed with reference to FIG. 4 may be used to providethis operation.

FIG. 6 shows generally a more detailed schematic of an example circuit600 that in one example could form a portion of the internal circuitryof a control circuit 615, which in one example could be control circuit115 in FIG. 1. The circuitry of FIG. 6 is one example of a circuit thatwhen coupled to receive a feedback signal representative of an outputvoltage of a power converter during a feedback portion T_(FB) of an offtime of a power switch could be used to regulate power delivery from aninput of a power converter to an output of the power converter.

As shown in the depicted example, control circuit 615 is coupled toreceive a feedback current I_(FB) 690 at feedback terminal 623. In oneexample, when feedback current I_(FB) 690 flows, the voltage V_(FB) 616of the feedback terminal 623 relative to ground terminal 624 issubstantially equal to a reference voltage Vref 664 plus the gatethreshold voltage of p channel transistor 650. Feedback current I_(FB)690 flows through transistor 650 and current source 651.

In operation, if feedback current I_(FB) 690 is greater than I3, thevoltage applied to the gates of transistors 656 and 657 is high andtransistor 657 is turned on. If feedback current signal I_(FB) 690 isless than I3, the voltage applied to the gates of transistors 656 and657 is low and transistor 656 is turned on. The remainder of the circuitoperation and its influence on output signal 622 duty cycle fromterminal 625 is similar to the circuitry described with respect to FIG.4 above. A circuit of the type shown in FIG. 6 could in one example beused to eliminate the need for a resistor divider, or resistor 112 asshown in FIG. 1 or resistor 512 as shown in FIG. 5. The choice of theremaining feedback resistors 111 and 511 in FIGS. 1 and 5 respectivelyis then made based on the known feedback voltages V_(FB) 116 and 516 inFIGS. 1 and 5, respectively, to regulate an output voltage of the powerconverter at a desired value. Although not shown in the schematic ofFIG. 6, additional components to compensate for voltage drop in theconnection between a power converter output and the load can beincluded, such as those described in connection with circuit elements470 and 471 in FIG. 4 in accordance with the teachings of the presentinvention.

FIG. 7 shows generally a flowchart describing one example method ofregulating power delivered from an input of a power converter to anoutput of the power converter. In the described method, the examplepower converter is similar to the power converters described above, inwhich there is switching of a power switch that is coupled to an energytransfer element coupled between the input and output of the powerconverter. In the example, the switching of the power switch iscontrolled with a control circuit coupled to the switch. A feedbacksignal is generated that is representative of a power converter outputvoltage during a feedback portion T_(FB) of the power switch off time.The control circuit is responsive to the feedback signal and the controlcircuit is coupled to control the switching of the power switch toregulate the relative time periods the feedback signal is above andbelow a threshold during the feedback portion T_(FB) of the power switchoff time.

In particular, as shown in the illustrated example in block 701, thepower switch is turned on. In bock 702, it is determined whether the ontime of the power switch is complete. When the power switch on time iscomplete, block 703 indicates that the power switch is turned off. It isnoted that completion of the power switch on time could be determinedbased on a variety of techniques such as for instance time measurementor based on the current flowing in the power switch reaching a thresholdvalue to name a few examples.

In block 704, it is detected whether the off time of the power switch iswithin the feedback portion T_(FB) of the power switch off time. If itis, it is detected in block 705 whether the feedback signal is above thethreshold value. If the feedback signal is above the threshold value,the feedback capacitor is discharged in block 706 (which in one examplemay be feedback capacitor 460 in FIG. 4 or 660 in FIG. 6) with a fixedcurrent. If the feedback signal is below the threshold value, thefeedback capacitor is charged in block 707 with a fixed current.

When it is detected in block 704 that the feedback portion T_(FB) of thepower switch off time is complete, the voltage appearing across thefeedback capacitor is detected in block 708. If this voltage isunchanged from the previous power switch switching cycle then the ontime duty cycle of the power switch is left unchanged and processing isreturned to block 701 through block 713, where again the power switch isturned on and the procedure is repeated. If, however, the feedbackcapacitor voltage is greater than the previous power switch switchingcycle as detected in block 710, processing proceeds to block 711 thesubsequent switching cycle on time is increased to increase duty cycle.It is noted that in other example control schemes, the power switch ontime could also be held constant and the overall power switch switchingcycle period could be reduced or a threshold of the current flowing inthe power switch could be increased to increase duty cycle in accordancewith the teachings of the present invention.

Continuing with the example, if it is detected in block 710 that thefeedback capacitor voltage is less than the previous power switchswitching cycle, processing proceeds to block 712 the subsequentswitching cycle on time is decreased to decrease duty cycle. It is notedthat in other control schemes, the power switch on time could also beheld constant and the overall power switch switching cycle periodincreased to decrease duty cycle in accordance with the teachings of thepresent invention. It is noted that the flowchart of FIG. 7 indicatesthe detection of capacitor voltage in block 708 when the feedbackportion T_(FB) of the power switch off time is complete as detected inblock 704. However in a circuit realization such as the examples shownin FIGS. 4 and 6, the duty cycle of the power switch is continuouslydetermined by the voltage across feedback capacitors 460 and 660throughout the switching cycle period of the power switch.

Using the example flowchart method of FIG. 7, therefore, the switchingof the power switch can be controlled to regulate the portions of thefeedback portion T_(FB) of the power switch off time that the feedbacksignal is above and below a threshold value in accordance with theteachings of the present invention.

FIG. 8 shows a more detailed example schematic of a circuit 800 that inone example could form a portion of the internal circuitry of controlcircuit 815, which in one example could be control circuit 115 in FIG. 1in accordance with the teachings of the present invention. The circuitryillustrated in FIG. 8 is another example of a circuit that, when coupledto receive a feedback signal representative of an output voltage of apower converter during a feedback portion T_(FB) of an off time of apower switch, could regulate power delivery from an input of a powerconverter to an output of the power converter in accordance with theteachings of the present invention.

It will be noted that the circuit depicted in FIG. 8 shares many aspectswith the example circuit of FIG. 4 and the description below willtherefore focus primarily on the differences in the circuit of FIG. 8compared to that in FIG. 4. As shown in the depicted example, controlcircuit 815 is coupled to receive a feedback signal V_(FB) 816. As inthe case of the circuit of FIG. 4, feedback voltage V_(FB) 816 iscompared to a reference voltage V_(REF) 852 using comparator 853. In oneexample, reference voltage V_(REF) 852 is equivalent to voltagethreshold value 201 in FIG. 2 and voltage threshold value 301 in FIG. 3.The output of comparator 853 is coupled to drive transistor switches 856and 857 to control a voltage 864 appearing across capacitor 860.

In common with the example circuit of FIG. 4, switch 859 is switchedsuch that switch 859 is in an on state only during the feedback portionT_(FB) of the power switch off time. Current can therefore only flowinto or out of feedback capacitor 860 during feedback portion T_(FB) ofthe power switch off time in the illustrated example. The voltageV_(PWM) 864 appearing across feedback capacitor 860 is coupled toamplifier circuit 877, which regulates the voltage appearing acrossresistor 880 to be substantially equal to the voltage across feedbackcapacitor 860. The value of resistor 880 therefore sets the value ofcurrent 879, which is in turn therefore responsive to the voltageappearing across feedback capacitor 860. Current 879 is mirrored bycurrent mirror 878 to produce control current signal 822 andcompensation current signal 887. Control current signal 822 is thereforealso responsive to the voltage appearing across capacitor 860.

In one example the duty cycle of power switch 105 in FIG. 1 isresponsive to control current signal 822 that in one example could becoupled to control the duty cycle of power switch 105 in FIG. 1 in orderto regulate power delivery from an input of a power converter to anoutput of the power converter in accordance with the teachings of thepresent invention. In one example the duty cycle of the power switch canbe controlled by controlling the peak value of current 104 flowing inpower switch 105 in FIG. 1. In another example the duty cycle of thepower switch can be controlled by controlling a switching cycle periodfor example T 212 in FIG. 2 while keeping an on time Ton 204substantially constant. In other examples, a combination of the above orother techniques can be used to control the duty cycle of the powerswitch in accordance with the teachings of the present invention.

The control circuit 815 therefore includes a first current source 858that is coupled to discharge feedback capacitor 860 through first switch857 during one portion of the feedback portion T_(FB) of the off time ofthe power switch and a second current source 855 that is coupled tocharge the feedback capacitor through second switch 856 during anotherportion of the feedback portion T_(FB) of the off time of the powerswitch. In one example the control current signal 822 is coupled to beresponsive to the voltage across the feedback capacitor 860 to control aduty cycle of the power switch to regulate power delivered from theinput to the output of the power supply.

In one example, the control circuit 815 further includes a voltagestabilization circuit 869 coupled to maintain a first voltage V1 893across the first current source 858 during an off time of the firstswitch 857 substantially equal to the voltage appearing across thefeedback capacitor 860. In the example, the voltage stabilizationcircuit 869 is further coupled to maintain a second voltage V2 892across the second current source 855 during an off time of the secondswitch 856 substantially equal to a difference between a control circuitsupply voltage 854 and the voltage appearing across the feedbackcapacitor 860.

As shown in the depicted example, compensation current signal 887 ismirrored by current mirror circuit 883 in order to provide cable anddiode drop compensation, as discussed above with reference to FIG. 4. Asshown in the example of FIG. 8, the mirrored current signal 890 iscoupled to non-inverting terminal 850 of comparator 853 with connection888. Current 890 is a combination of diode drop compensation currentflowing in transistor 881 and cable drop compensation current flowing intransistor 884. The relative magnitude of diode and cable dropcompensation signals can be determined by the appropriate sizing oftransistors 884 and 881. In one example, the low pass filter 882 iscoupled to filter the cable drop compensation signal to improve powerconverter stability. In one example therefore, transistors 884 and 881provide a parallel impedance to external feedback impedances 811 and812, which in one example are equivalent to feedback resistors 111 and112 in FIG. 1.

By varying the compensation current 890, the effective ratio of theresistor divider formed by resistors 811 and 812 is varied in turnvarying the relationship between V_(out) 889 and V_(FB) 816, whereV_(out) is a voltage representative of an output of the power converterduring an off time of the power switch, to compensate for cable anddiode voltage drops in the output circuitry of the power converter. Inone example, with the cable and diode drop compensation techniquedescribed above, the degree of compensation can be selected by theappropriate choice of external resistors 811 and 812. If low values ofresistors 811 and 812 are chosen, the diode and cable drop compensationsignal current 890 will have less effect than if larger values forexternal resistors 811 and 812 are chosen.

The example circuit of FIG. 8 also includes the voltage stabilizationcircuit block 869 used to increase the accuracy of circuit 815 ifdesired. Without the voltage stabilization circuit 869, the voltageacross current sources 855 and 858 may change when the switches 856 and857 turn on and off. This may introduce an initial error in charge anddischarge currents of practical current source circuits when theswitches 856 and 857 again turn on during the next power switchswitching cycle. These initial current errors may reduce the accuracywith which charging and discharging currents flowing in capacitor 860are established, which may reduce the accuracy with which the powerconverter output voltage is regulated.

In order to help maintain the voltage drop substantially constantwhether switches 856 and 857 are on or off, voltage stabilizationcircuit 869 establishes a voltage at node 872 when switch 856 is off,that is substantially equal to the voltage at node 872 when switch 856is on. Similarly circuit 869 establishes a voltage at node 874 whenswitch 857 is off, that is substantially equal to the voltage at node874 when switch 857 is on. This performance is provided by the unitygain amplifier 875, the output of which is held at the voltage acrossfeedback capacitor 860 through connection 871. The output of unity gainamplifier is coupled to node 872 when switch 856 turns off and iscoupled to node 874 when switch 857 turns off. In this way, currentsources 855 and 858 establish their regulated current value flowing infeedback capacitor 860 substantially immediately such that switches 856,857 and 859 provide a current path for current to flow in feedbackcapacitor 860.

The circuit of FIG. 8 also shows parallel current sources 870 and 873 tocurrent sources 855 and 858, respectively. In one example these currentsources are responsive to the current control signal 822. In oneexample, current sources 870 and 873 are turned on when current controlsignal 822 reaches a threshold value. In one example the magnitude ofcurrent flowing in current sources 870 and 873 is responsive to thevalue of current control signal 822. In one example, parallel currentsources 870 and 873 provide increased gain to increase the speed withwhich capacitor 860 is charged and discharged. In one example, thisincreased gain is used under light load conditions in the powerconverter operation when the duration of T_(FB) 205 or 305 is veryshort. The increased gain provided with parallel current sources 870 and873 helps improve the transient response of the power converter tochanges in load conditions at the output of the power converter. In oneexample, current sources 870 and 873 provide currents substantiallyequal in value and substantially equal to up to 9 times the currentvalues of current sources 855 and 858.

In the above descriptions of control circuits 415, 615 and 815, a dutycycle of a power switch to regulate an output of a power converter isresponsive to a voltage across a capacitor 460, 660 and 860,respectively, in FIGS. 4, 6 and 8. It is noted, however, that the dutycycle of a power switch could alternatively be responsive to a value ofa digital counter circuit while still benefiting from the teachings ofthe present invention. In one example a digital counter circuit could bedecremented at a frequency higher than the power switch switchingfrequency, for the portion of the feedback portion T_(FB) of the offtime of the power switch that the feedback signal is above a thresholdvalue and incremented at a frequency higher than the power switchswitching frequency, for the portion of the feedback portion T_(FB) ofthe off time of the power switch that the feedback signal is below athreshold value, where the switching frequency is the reciprocal of thepower switch switching cycle period. In this example, the value of thedigital counter count at the end of the feedback portion T_(FB) of theoff time of the power switch could then be used to set a duty cycle ofthe power switch for one or more forthcoming switching cycle periods. Itis noted that other techniques could be used as alternatives to theabove descriptions for regulating the portions of the feedback portionT_(FB) of the power switch off time that the feedback signal is aboveand below the threshold value while still benefiting from the broaderteachings of the present invention.

The above description of illustrated examples of the present invention,including what is described in the Abstract, are not intended to beexhaustive or to be limitation to the precise forms disclosed. Whilespecific embodiments of, and examples for, the invention are describedherein for illustrative purposes, various equivalent modifications arepossible without departing from the broader spirit and scope of thepresent invention. Indeed, it is appreciated that the specific voltages,currents, frequencies, power range values, times, etc., are provided forexplanation purposes and that other values may also be employed in otherembodiments and examples in accordance with the teachings of the presentinvention.

These modifications can be made to examples of the invention in light ofthe above detailed description. The terms used in the following claimsshould not be construed to limit the invention to the specificembodiments disclosed in the specification and the claims. Rather, thescope is to be determined entirely by the following claims, which are tobe construed in accordance with established doctrines of claiminterpretation. The present specification and figures are accordingly tobe regarded as illustrative rather than restrictive.

What is claimed is:
 1. A power converter, comprising: an energy transferelement coupled between a power converter input and a power converteroutput; a power switch coupled to the energy transfer element; and acontrol circuit coupled to receive a feedback signal representative ofthe power converter output during a feedback portion of an off time ofthe power switch, wherein the control circuit is coupled to generate anoutput signal in response to the feedback signal, wherein the outputsignal is coupled to be received by the power switch to controlswitching of the power switch to control a fraction of the feedbackportion of the off time of the power switch that the feedback signal isabove a threshold and another fraction of the feedback portion of theoff time of the power switch that the feedback signal is below thethreshold.
 2. The power converter of claim 1 wherein the control circuitcomprises a feedback capacitor coupled to be discharged when thefeedback signal is above the threshold during the feedback portion ofthe off time of the power switch and wherein the feedback capacitor iscoupled to be charged when the feedback signal is below the thresholdduring the feedback portion of the off time of the power switch.
 3. Thepower converter of claim 2 wherein the control circuit further comprisesfirst and second current sources coupled to charge and discharge thefeedback capacitor in response to the feedback signal.
 4. The powerconverter of claim 3 wherein the control circuit further comprises avoltage stabilization circuit coupled to the first and second currentsources to stabilize first and second voltages across the first andsecond current sources, respectively.
 5. The power converter of claim 4wherein the voltage stabilization circuit comprises an amplifier havingan input coupled to the feedback capacitor, wherein the amplifier has anoutput that is coupled to either the first current source or the secondcurrent source in response to whether the feedback capacitor is coupledto be charged or discharged, respectively.
 6. The power converter ofclaim 1 wherein the feedback signal is a feedback voltage.
 7. The powerconverter of claim 1 wherein the feedback signal is a feedback current.8. The power converter of claim 1 wherein the control circuit comprisesa pulse width modulator comparator coupled to generate the output signalin response to the feedback signal.
 9. The power converter of claim 1wherein the control circuit comprises a cable drop compensation circuitcoupled to compensate for a voltage drop due to a cable impedance in thepower converter output, wherein the cable drop compensation circuitcomprises a first current minor circuit coupled to conduct a cable dropcompensation current signal that is response to the feedback signal anda filter coupled to the first current minor circuit.
 10. The powerconverter of claim 1 wherein the control circuit comprises a diode dropcompensation circuit coupled to compensate for a voltage drop due to adiode impedance in the power converter output, wherein the diode dropcompensation circuit comprises a second current minor circuit coupled toconduct a diode drop compensation current signal that is responsive tothe feedback signal.